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semiconductor technical data critical conduction greenline ? smps controller d1, d2 suffix plastic package case 751 (so8) 16 1 pin connections order this document by mc33364/d d suffix plastic package case 751b (so16) 8 1 MC33364D1 mc33364d2 mc33364d 18 7 6 5 2 3 4 (top view) zero current current sense voltage fb line v ref p gnd gate drive v cc 116 13 12 11 10 9 2 3 4 5 6 7 8 (top view) zero current n/c current sense v ref n/c freq clamp line a gnd voltage fb n/c p gnd gate drive p v cc a v cc 1 motorola analog ic device data
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the mc33364 series are variable frequency smps controllers that operate in the critical conduction mode. they are optimized for low power, high density power supplies requiring minimum board area, reduced component count, and low power dissipation. each narrow body soic package provides a small footprint. integration of the high voltage startup saves approximately 0.7 w of power compared to resistor bootstrapped circuits. each mc33364 features an onboard reference, uvlo function, a watchdog timer to initiate output switching, a zero current detector to ensure critical conduction operation, a current sensing comparator, leading edge blanking, and a cmos driver. protection features include the ability to shut down switching, and cyclebycycle current limiting. the MC33364D1 is available in a surface mount so8 package. it has an internal 126 khz frequency clamp. for loads which have a low power operating condition, the frequency clamp limits the maximum operating frequency, preventing excessive switching losses and emi radiation. the mc33364d2 is available in the so8 package without an internal frequency clamp. the mc33364d is available in the so16 package. it has an internal 126 khz frequency clamp which is pinned out, so that the designer can adjust the clamp frequency by connecting appropriate values of resistance. ? lossless offline startup ? leading edge blanking for noise immunity ? watchdog timer to initiate switching ? minimum number of support components ? shutdown capability ? over temperature protection ? optional frequency clamp ordering information device operating temperature range package MC33364D1 t25 125 c so8 mc33364d2 t j = 25 to +125 c so8 mc33364d so16 representative block diagram this device contains 335 active transistors. current sense fb zc det v cc gate pwm comparator s r q gnd line v ref v ref uvlo restart delay r leading edge blanking zero current detector watchdog timer thermal shutdown bandgap reference v cc uvlo frequency clamp optional frequency clamp this document contains information on a new product. specifications and information herein are subject to change without notice. ? motorola, inc. 1997 rev 0
mc33364 2 motorola analog ic device data maximum ratings (t a = 25 c, unless otherwise noted.) rating symbol value unit power supply voltage (transient) v cc 20 v power supply voltage (operating) v cc 16 v line voltage v line 700 v current sense, compensation, voltage feedback, restart delay and zero current input voltage v in1 1.0 to +10 v zero current detect input i in 5.0 ma restart diode current i in 5.0 ma power dissipation and thermal characteristics d1 and d2 suffix, plastic package case 751 maximum power dissipation @ t a = 70 c p d 450 mw thermal resistance, junctiontoair r q ja 178 c/w d suffix, plastic package case 751b05 maximum power dissipation @ t a = 70 c p d 550 mw thermal resistance, junctiontoair r q ja 145 c/w operating junction temperature t j 150 c operating ambient temperature t a 25 to +125 c storage temperature range t stg 55 to +150 c note: esd data available upon request. electrical characteristics (v cc = 12 v, for typical values t a = 25 c, for min/max values t j = 25 to 125 c) characteristic symbol min typ max unit voltage reference reference output voltage (i out = 0 ma, t j = 25 c) v ref 4.90 5.05 5.20 v line regulation (v cc = 10 v to 20 v) reg line 2.0 50 mv load regulation (i out = 0 ma to 5.0 ma) reg load 0.3 50 mv maximum v ref output current i o 5 ma reference undervoltage lockout threshold v th 4.5 v zero current detector input threshold voltage (v in increasing) v th 0.9 1.0 1.1 v hysteresis (v in decreasing) v h 200 mv input clamp voltage v high state (i det = 3.0 ma) v ih 9.0 10.33 12 low state (i det = 3.0 ma) v il 0.5 0.75 1.1 current sense comparator input bias current (v cs = 0 to 2.0 v) i ib 0.5 0.02 0.5 m a built in offset v io 50 108 170 mv feedback pin input range v fb 1.1 1.24 1.4 v feedback pin to output delay t dly 100 232 400 ns drive output source resistance (drive = 0 v, v gate = v cc 1.0 v) r oh 10 36 70 w sink resistance (drive = v cc , v gate = 1.0 v) r ol 5 11 25 w output voltage rise time (25% 75%) (c l = 1.0 nf) t r 67 150 ns output voltage fall time (75% 25%) (c l = 1.0 nf) t f 28 50 ns output voltage in undervoltage (v cc = 7.0 v, i sink = 1.0 ma) v o(uv) 0.01 0.03 v
mc33364 3 motorola analog ic device data electrical characteristics (continued) (v cc = 12 v, for typical values t a = 25 c, for min/max values t j = 25 to 125 c) characteristic unit max typ min symbol leading edge blanking delay to current sense comparator input t phl(in/out) 250 ns (v fb = 2.0 v, v cs = 0 v to 4.0 v step, c l = 1.0 nf) timer watchdog timer t dly 200 410 700 m s undervoltage lockout startup threshold (v cc increasing) v th(on) 14 15 16 v minimum operating voltage after turnon (v cc decreasing) v shutdown 6.5 7.6 8.5 v frequency clamp internal fc function (pin open) f max 90 126 160 khz internal fc function (pin grounded) f max 400 564 700 khz frequency clamp input threshold v th(fc) 2.0 v frequency clamp control current range i control 30 70 110 m a total device line startup current (v line = 50 v) (v cc = v th(on) 1.0 v) i line 5.0 8.5 12 ma restart delay time t dly 100 ms line pin leakage (v line = 575 v) i line 0.5 32 70 m a line startup current (v cc = 0 v, v line = 50 v) i line 6.0 10 12 ma v cc dynamic operating current (50 khz, c l = 1.0 nf) v cc static operating current (v cc = 16 v, v ref = 0) i cc 1.5 2.75 3.0 4.5 ma v cc pin leakage (v cc = 11 v) i cc lkg 300 544 800 m a
mc33364 4 motorola analog ic device data 0.1 t d , programmed dead time ( sec) i in , current sourced into pin 8 ( m a) 0.1 1.0 10 100 100 0 m 55 16 v fb , voltage feedback d t a , ambient temperature ( c) v cc = 14 v threshold change (mv) 12 8.0 4.0 5.0 4.0 25 0 25 50 75 125 100 55 500 t dly , watchdog time delay ( s) t a , ambient temperature ( c) m 450 400 350 300 25 0 25 50 75 100 12 5 v cc = 14 v figure 1. drive output waveform figure 2. watchdog timer delay versus temperature figure 3. reference voltage versus temperature 25 output voltage (v) 5.0 m s/div 20 15 10 0 5.0 4.0 6.0 i cc , supply current (ma) v cc , supply voltage (v) circuit of figure 7 t a = 25 c 4.0 2.0 0 6.0 8.0 10 12 14 16 figure 4. supply current versus supply voltage 0.01 1000 r ja(t) , thermal resistance t, time (s) q junctiontoair ( c/w) 100 10 0.1 1.0 10 100 figure 5. transient thermal resistance d suffix 16 pin soic figure 6. dead time versus input current d suffix 16 pin soic t a = 25 c v cc = 14 v 1.0 10 100 1000 v cc = 14 v c l = 1000 pf t a = 25 c 30 5.0
mc33364 5 motorola analog ic device data functional description introduction with the goal of reducing the size and cost of offline power supplies, there is an ever increasing demand for an economical method of obtaining a regulated galvanically isolated dc output voltage using a control which operates directly from the ac line. this data sheet describes a monolithic control ic that was specifically designed for power supply control with a minimal number of external components. it offers the designer a simple cost effective solution to obtain the benefits of offline power regulation. figure 7. functional block diagram s r r 5.0 v reference u3 moc8102 c3 20 mtd1n60 q1 + c5 300 t1 470 r4 r3 1.2 k r5 47 k r2 22 k r7 2.2 r10 14 k r8 430 c8 330 pf 6.0 v 2 amp c7 10 c4 .001 c9 .01 c10 0.1 1 2 4 5 u2 tl431 2 1 3 1n4934 d5 d6 murs160t3 d7 1n4148 d8 mbrs340t3 r1 56 r6 47 k r9 39 k r11 10 k r12 100 zero current detect v ref current sense frequency clamp gate drive zero current v cc line + 15/7.6 uvlo 0.3/ 0.25 v voltage fb p gnd 5.0 v 4.0 k 10 pf 3.0 m a leading edge blanking uvlo v cc p v cc a gnd mc33364 en 5.0 k 14 k 1.5 v emi filter 92 to 270 vac c5 10 d1 1n4006 d3 1n4006 1n4006 d2 d4 1n4006 10 v 2.0 v 44 k 2.0 v d9 1n4148 r13 100 r q timer q r q s q en + c2 0.01 v o 2.5 r10 r11 1 operating description the mc33364 contains many of the building blocks and protection features that are employed in modern high performance current mode power supply controllers. referring to the block diagram in figure 7, note that this device does not contain an oscillator. a description of each of the functional blocks is given below. zero current detector the mc33364 operates as a critical conduction current mode controller, whereby output switch conduction is initiated by the zero current detector and terminated when the peak inductor current reaches the input threshold level. the zero current detector initiates the next ontime by setting the rs latch at the instant the inductor current reaches zero. this critical conduction mode of operation has two significant benefits. first, since the mosfet cannot turnon until the inductor current reaches zero, the output rectifier's reverse recovery time becomes less critical allowing the use of an inexpensive rectifier. second, since there are no deadtime gaps between cycles, the ac line current is continuous thus limiting the peak switch to twice the average input current the zero current detector indirectly senses the inductor current by monitoring when the auxiliary winding voltage falls below 0.25 v. to prevent false tripping, 50 mv of hysteresis is provided. the zero current detector input is internally
mc33364 6 motorola analog ic device data protected by two clamps. the upper 0.7 v clamp prevents input overvoltage breakdown while the lower 0.7 v clamp prevents substrate injection. an external resistor must be used in series with the auxiliary winding to limit the current through the clamps to 5.0 ma or less. current sense comparator and rs latch the current sense comparator rs latch configuration used ensures that only a single pulse appears at the drive output during a given cycle. the inductor current is converted to a voltage by inserting a groundreferenced sense resistor in series with the source of output switch. this voltage is monitored by the current sense input and compared to the divided down feedback voltage. the internal feedback voltage divider is limited to 1.5 v maximum. therefore the maximum peak switch current is: i pk(max) 1.5 v r sense the current sense input to drive output propagation delay is typically 232 ns. timer a watchdog timer function was added to the ic to eliminate the need for an external oscillator when used in stand alone applications. the timer provides a means to automatically start or restart the preconverter if the drive output has been off for more than 410 microseconds after the inductor current reaches zero. undervoltage lockout the mc33364 has a 5.0 v internal reference brought out to pin 6 (d suffix) or pin 4 (d1 and d2 suffixes) and capable of sourcing 10 ma typically. it also contains an under voltage lockout (uvlo) circuit which suppresses the gate output at pin 11 if the v cc supply voltage drops below 7.6 v typical. restart delay a restart delay function is provided to allow hiccup mode fault protection in case of a short circuit condition and to prevent the smps from repeatedly trying to restart after the input line voltage has been removed. when power is first applied, the v cc bypass capacitor is charged through a constant current source. the restart delay turns off the high voltage startup mosfet when v cc reaches the startup threshold level. the restart delay turns on the high voltage mosfet after v cc has dropped below 4.5 v. if the smps output is short circuited, the transformer winding, which provides the v cc voltage to the mc33364, will be unable to sustain v cc . the restart delay prevents the high voltage startup transistor within the ic from maintaining the voltage on the v cc pin bootstrap capacitor. after v cc drops below the uvlo threshold in the smps, the smps switching transistors are held off for the time programmed by the restart delay circuit. in this manner, the smps switching transistor is operated at a very low duty cyle, preventing destruction. if the short circuit fault is removed, the power supply system will turn on by itself in a normal startup mode after the restart delay has timed out figure 8. frequency clamp circuit frequency clamp gate drive signal fc output to pwm latch 4.0 k 10 pf 2.0 v 5.0 v 3.0 m a 0 = disable 2.0 v output switching frequency clamp in normal operation, the mc33364 operates the flyback transformer primary inductance in the critical mode. that is, the inductor current ramps to a peak value, ramps down to zero, then immediately begins ramping positive again. the peak current is programmed by the current sense resistance value. if the output load is reduced from full load to a standby load or no load condition, the switching frequency can increase to hundreds of kilohertz. because regulatory agency emi limits for allowed conducted current decreases as the switching frequency increases beyond 150 khz, this may be an undesireable operating condition. the output switching frequency clamp remedies this situation to minimize emi generated in this operating region. the internal frequency clamp circuit in the MC33364D1 and mc33364d programs a minimum off time, forcing discontinuous mode operation and limiting the operating frequency to less than 126 khz. the mc33364d2 does not contain a frequency clamp circuit. the output switching frequency clamp function in the mc33364d can be disabled by connecting the fc input, pin 8, to ground. the clamp frequency can be set externally by sinking or sourcing a current into the pin of up to 100 microamperes. output the ic contains a cmos output driver specifically designed for direct drive of power mosfets. the drive output is capable of up to 1500 ma peak current with a typical rise and fall time of 50 ns with a 1.0 nf load. additional internal circuitry has been added to keep the drive output in a sinking mode whenever the undervoltage lockout is active. this characteristic eliminates the need for an external gate pulldown resistor. the totempole output has been optimized to minimize crossconduction current during high speed operation. design example design an offline flyback converter according to the following requirements: output power: 12 w output: 6.0 v @ 2 amperes input voltage range: 90 vac 270 vac, 50/60 hz the operation for the circuit shown in figure 9 is as follows: the rectifier bridge d1d4 and the capacitor c1 convert the ac line voltage to dc. this voltage supplies the primary winding of the transformer t1 and the startup circuit
mc33364 7 motorola analog ic device data in u1 through pin 8. the primary current loop is closed by the transformer's primary winding, the tmos switch q1 and the current sense resistor r7. the switch q1 is driven from pin 6 of u1 through the resistor r4 and the diode d7. the resistor r4 smooths the switchon of q1. the diode d7 ensures a fast switchingoff. the resistors r5, r6, diode d6 and capacitor c4 create a clamping network that protects q1 from spikes on the primary winding. the network consisting of capacitor c3, diode d5 and resistor r1 provides a v cc supply voltage for u1 from the auxiliary winding of the transformer. the resistor r1 makes v cc more stable and resistant to noise. the resistor r2 reduces the current flow through the internal clamping and protection zener diode of the zero crossing detector (zcd) within u1. c3 is the decoupling capacitor of the supply voltage. the resistor r3 provides bias current for the optoisolator's transistor. the diode d8 and the capacitor c5 rectify and filter the output voltage. the device u2 drives the primary side through the optoisolator to make the output voltage stable. the output voltage information is delivered to u2 by a resistive divider that consists of resistors r10 and r11. the resistor r9 and the capacitors c7, c8 provide frequency compensation of the feedback loop. since the critical conduction mode converter is a variable frequency system, the mc33364 has a builtin special block to reduce switching frequency in the no load condition. this block is named the ofrequency clampo block. mc33364 used in the design example has an internal frequency clamp set to 126 khz. however, optional versions with a disabled or variable frequency clamp are available. the frequency clamp works as follows: the clamp controls the part of the switching cycle when the mosfet switch is turned off. if this oofftimeo (determined by the reset time of the transformer's core) is too short, then the frequency clamp does not allow the switch to turnon again until the defined frequency clamp time is reached (i.e., the frequency clamp will insert a dead time). there are several advantages of the mc33364's startup circuit. the startup circuit includes a special high voltage switch that controls the path between the rectified line voltage and the v cc supply capacitor to charge that capacitor by a limited current when the power is applied to the input. after a few switching cycles the ic is supplied from the transformer's auxiliary winding. after v cc reaches the undervoltage lockout threshold value, the startup switch is turned off by the undervoltage and the overvoltage control circuit. because the power supply can be shorted on the output, causing the auxiliary voltage to be zero, the mc33364 will periodically start its startup block. this mode is named ohiccup modeo. during this mode the temperature of the chip rises but remains protected by the thermal shutdown block. during the power supply's normal operation, the high voltage internal mosfet is turned off, preventing wasted power, and thereby, allowing greater circuit efficiency. since a bridge rectifier is used, the resulting minimum and maximum dc input voltages can be calculated: v in(min) dc 2 xv in(min) ac 2 ( 90 vac ) 127 v v in( ax) dc 2 xv in( ax) ac 2 ( 270 vac ) 382 v the maximum average input current is: i in p out nv in(min) 12 w [ 0.8 ( 127 v )] 0.118 a where n = estimated circuit efficiency. a tmos switch with 600 v avalanche breakdown voltage is used. the voltage on the switch's drain consists of the input voltage and the flyback voltage of the transformer's primary winding. there is a ringing on the rising edge's top of the flyback voltage due to the leakage inductance of the transformer. this ringing is clamped by the rcd network. design this clamped wave for an amplitude of 50 v. add another 50 v to allow a safety margin for the mosfet. then a suitable value of the flyback voltage may be calculated: v flbk v tmos v in(max) 100 v 600 v 382 v 100 v 118 v since this value is very close to the v in(min) , set: v flbk v in(min) 127 v the v flbk value of the duty cycle is given by: max v flbk v flbk v in(min) 127 v [ 127 v 127 v ] 0.5 the maximum input primary peak current: i ppk 2i in [ max ] 0.2 ( 0.118 a ) 0.5 0.472 a choose the desired minimum frequency f min of operation to be 70 khz . after reviewing the core sizing information provided by a core manufacturer, a ee core of size about 20 mm was chosen. siemens' n67 magnetic material is used, which corresponds to a philips 3c85 or tdk pc40 material. the primary inductance value is given by: l p max v in(min) i ppk f min 0.5 ( 127 v ) ( 0.472 a )( 70 khz ) 1.92 mh the manufacturer recommends for that magnetic core a maximum operating flux density of: b max 0.2 t the crosssectional area a c of the ef20 core is: a c 33.5 mm 2 the operating flux density is given by: b max l p i ppk n p a c from this equation the number of turns of the primary winding can be derived: n p l p i ppk b max a c
mc33364 8 motorola analog ic device data the a l factor is determined by: a l l p n 2 p l p b max a c
2 l p i ppk
2 0.2 t
33.5 e6 m 2
2 .00192 h
( 0.472 a ) 2 105 nh from the manufacturer`s catalogue recommendation the core with an a l of 100 nh is selected. the desired number of turns of the primary winding is: n p l p a l
1 2 ( 0.00192 h ) ( 100 nh ) 1 2 139 turns the number of turns needed by the 6.0 v secondary is (assuming a schottky rectifier is used): n s v s v fwd
1 max
n p max v in(min)
6.0 v 0.3 v
1 0.5
139 0.5 127 v
7 turns the auxiliary winding to power the control ic is 16 v and its number of turns is given by: naux (v aux v fwd )(1 max)n p max(v in(min) ) (16 v 0.9 v)(1 0.5)139 [0.5(127 v)] 19 turns the approximate value of rectifier capacitance needed is: c1 t off (i in ) v ripple (5 m sec)(0.118 a) 50 v 11.8 f where the minimum ripple frequency is 2 times the 50 hz line frequency and t off , the discharge time of c1 during the haversine cycle, is assumed to be half the cycle period. because we have a variable frequency system, all the calculations for the value of the output filter capacitors will be done at the lowest frequency, since the ripple voltage will be greatest at this frequency. the approximate equation for the output capacitance value is given by: c5 i out (f min )(v rip ) 2a (70 khz)(0.1 v) 286 f determining the value of the current sense resistor (r7), one uses the peak current in the predesign consideration. since within the ic there is a limitation of the voltage for the current sensing, which is set to 1.2 v, the design of the current sense resistor is simply given by: r7 v cs i ppk 1.2 v 0.472 a 2.54 2.2 the error amplifier function is provided by a tl431 on the secondary, connected to the primary side via an optoisolator, the moc8102. the voltage of the optoisolator collector node sets the peak current flowing through the power switch during each cycle. this pin will be connected to the feedback pin of the mc33364, which will directly set the peak current. starting on the secondary side of the power supply, assign the sense current through the voltagesensing resistor divider to be approximately 0.25 ma. one can immediately calculate the value of the lower and upper resistor: r lower r11 v ref (tl431) i div 2.5 v 0.25 ma 10 k r upper r10 v out v ref (tl431) i div 6.0 v 2.5v 0.25 ma 14 k the value of the resistor that would provide the bias current through the optoisolator and the tl431 is set by the minimum operating current requirements of the tl431. this currernt is minimum 1.0 ma. assign the maximum current through the branch to be 5 ma. that makes the bias resistor value equal to: r bias r s v out [v ref (tl431) v led ] i led 6.0 v [2.5v 1.4v] 5.0 ma 420 430 the moc8102 has a typical current transfer ratio (ctr) of 100% with 25% tolerance. when the tl431 is fullon, 5 ma will be drawn from the transistor within the moc8102. the transistor should be in saturated state at that time, so its collector resistor must be r collector v ref v sat i led 5.0 v 0.3 v 5.0 ma 940 since a resistor of 5.0 k is internally connected from the reference voltage to the feedback pin of the mc33364, the external resistor can have a higher value r ext r3 (r int )(r collector ) (r int ) (r collector ) (5.0 k)(940) 5.0 k 940 1157 1200 this completes the design of the voltage feedback circuit. in no load condition there is only a current flowing through the optoisolator diode and the voltage sense divider on the secondary side. the load at that condition is given by: r noload v out (i led i div ) 6.0 v (5.0 ma 0.25 ma) 1143 the output filter pole at no load is: f pn 1 (2 r noload c out ) 1 (2 )(1143)(300 f) 0.46 hz
mc33364 9 motorola analog ic device data in heavy load condition the i led and i div is negligible. the heavy load resistance is given by: r heavy v out i out 6.0 v 2.0 a 3.0 the output filter pole at heavy load of this output is f pn 1 (2 r heavy c out ) 1 (2 )(3)(300 f) 177 hz the gain exhibited by the open loop power supply at the high input voltage will be: a v in max v out 2 ns (v in max )(v error )(np) ( 382 v 6.0 v ) 2 (7) (382 v)(1.2 v)(139) 15.53 23.82 db the maximum recommended bandwidth is approximately: f c fs min 5 70 khz 5 14 khz the gain needed by the error amplifier to achieve this bandwidth is calculated at the rated load because that yields the bandwidth condition, which is: gc 20 log f c f ph a 20 log 14 khz 177 23.82 db 14.14 db the gain in absolute terms is: a c 10 (gc 20) 10 (14.14 20) 51 now the compensation circuit elements can be calculated. the output resistance of the voltage sense divider is given by the parallel combination of resistors in the divider: r in r upper || r lower 10 k || 14 k 5833 r9 (ac) (r in ) 29.75 k 30 k c8 1 2 (a c )(r in )(f c ) 382 pf 390 pf the compensation zero must be placed at or below the light load filter pole: c7 1 2 (r9) (f pn ) 11.63 f 10 f
mc33364 10 motorola analog ic device data figure 9. 12 w power supply line regulation i o = 930 ma line regulation v in = 115 vrms output ripple efficiency v in = 90 to 270 vac d = 78 mv or 6.5% i o = 110 to 1100 ma d = 103 mv or 8.6% v in = 115 vac, i o = 1100 ma v in = 115 vac, i o = 1100 ma 600 mvpp 72.9% s r r 5.0 v reference u3 moc8102 c3 20 mtd1n60 q1 + c5 300 t1 470 r4 r3 1.2 k r5 47 k r2 22 k r7 2.2 r10 14 k r8 430 c8 330 pf 6.0 v 2 amp c7 10 c4 .001 c9 .01 c10 0.1 1 2 4 5 u2 tl431 2 1 3 1n4934 d5 d6 murs160t3 d7 1n4148 d8 mbrs340t3 r1 56 r6 47 k r9 30 k r11 10 k r12 100 zero current detect v ref current sense frequency clamp gate drive zero current v cc line + 15/7.6 uvlo 0.3/ 0.25 v voltage fb p gnd 5.0 v 4.0 k 10 pf 3.0 m a leading edge blanking uvlo v cc p v cc a gnd u1 mc33364 en 5.0 k 14 k 1.5 v emi filter 92 to 270 vac c1 10 d1 1n4006 d3 1n4006 1n4006 d2 d4 1n4006 10 v 2.0 v 44 k 2.0 v d9 1n4148 r13 100 r q timer q r q s q en + c2 0.01
mc33364 11 motorola analog ic device data c3 0.1 m f j1 line d1 b250r c1 f1 t 0.2 a 8 line 7v cc 1 zcd gate 6 cs 2 4 v ref gnd 5 c2 20 m f r1 220 d3 1n4148 d2 b2x84c18lt1 r5 47 k r4 47 k c4 1.0 nf q1 mtd1n60e r4 47 k u1 MC33364D1 54 1 2 j2 543 2 7 9 d6 murs320t3 d7 1n4148 r7 100 d8 b2x84c5v1lt1 c6 1.0 m f r8 4.7 k c5 100 m f u2 mc33341 8 7 6 54 3 2 1 v cc gnd v s csb do cmp cta csa r12 82 k r11 10 k r13 22 k r3 22 k r10 0.25 r9 100 c7 33 nf 3 fb figure 10. universal input battery charger 12 10 m f 350 v 18 v t1 d5 murs 160t3 12 5.1 v t1 = 139 turns #28 awg, primary winding 2 3 7 turns, bifilar 2 x #26 awg, output winding 9 7 19 turns #28 awg, auxiliary winding 4 5 on philips ef203c85 core gap for a primary inductor of 1.92 mh. output 12 v @ 0.8 amp max input voltage range 90 270 vac, 50/60 hz u3 moc8102
mc33364 12 motorola analog ic device data d1, d2 suffix plastic package case 75105 (so8) issue s d suffix plastic package case 751b05 (so16) issue j outline dimensions seating plane 1 4 5 8 a 0.25 m cb ss 0.25 m b m h c x 45 l dim min max millimeters a 1.35 1.75 a1 0.10 0.25 b 0.35 0.49 c 0.18 0.25 d 4.80 5.00 e 1.27 bsc e 3.80 4.00 h 5.80 6.20 h 0 7 l 0.40 1.25 0.25 0.50 notes: 1. dimensioning and tolerancing per asme y14.5m, 1994. 2. dimensions are in millimeters. 3. dimension d and e do not include mold protrusion. 4. maximum mold protrusion 0.15 per side. 5. dimension b does not include mold protrusion. allowable dambar protrusion shall be 0.127 total in excess of the b dimension at maximum material condition. d e h a b e b a1 c a 0.10 notes: 1. dimensioning and tolerancing per ansi y14.5m, 1982. 2. controlling dimension: millimeter. 3. dimensions a and b do not include mold protrusion. 4. maximum mold protrusion 0.15 (0.006) per side. 5. dimension d does not include dambar protrusion. allowable dambar protrusion shall be 0.127 (0.005) total in excess of the d dimension at maximum material condition. 18 16 9 seating plane f j m r x 45 g 8 pl p b a m 0.25 (0.010) b s t d k c 16 pl s b m 0.25 (0.010) a s t dim min max min max inches millimeters a 9.80 10.00 0.386 0.393 b 3.80 4.00 0.150 0.157 c 1.35 1.75 0.054 0.068 d 0.35 0.49 0.014 0.019 f 0.40 1.25 0.016 0.049 g 1.27 bsc 0.050 bsc j 0.19 0.25 0.008 0.009 k 0.10 0.25 0.004 0.009 m 0 7 0 7 p 5.80 6.20 0.229 0.244 r 0.25 0.50 0.010 0.019
mc33364 13 motorola analog ic device data motorola reserves the right to make changes without further notice to any products herein. motorola makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does motorola assume any liability arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation consequential or incidental damages. atypicalo parameters which may be provided in motorola data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. all operating parameters, including atypicalso must be validated for each customer application by customer's technical experts. motorola does not convey any license under its patent rights nor the rights of others. motorola products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other applications intended to support or sustain life, or for any other application in which the failure of the motorola product could create a situation where personal injury or death may occur. should buyer purchase or use motorola products for any such unintended or unauthorized application, buyer shall indemnify and hold motorola and its officers, employees, subsidiaries, affiliates, and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, directly or indirectly, any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim alleges that motorola was negligent regarding the design or manufacture of the part. motorola and are registered trademarks of motorola, inc. motorola, inc. is an equal opportunity/affirmative action employer.
mc33364 14 motorola analog ic device data mfax is a trademark of motorola, inc. how to reach us: usa / europe / locations not listed : motorola literature distribution; japan : nippon motorola ltd.: spd, strategic planning office, 4321, p.o. box 5405, denver, colorado 80217. 13036752140 or 18004412447 nishigotanda, shinagawaku, tokyo 141, japan. 81354878488 customer focus center: 18005216274 mfax ? : rmfax0@email.sps.mot.com touchtone 1 6022446609 asia / pacific : motorola semiconductors h.k. ltd.; 8b tai ping industrial park, motorola fax back system us & canada only 18007741848 51 ting kok road, tai po, n.t., hong kong. 85226629298 http://sps.motorola.com/mfax/ home page : http://motorola.com/sps/ mc33364/d ?

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